Automatic modulation control of sync suppressed television signals

ABSTRACT

The depth of modulation and the absolute RF carrier level of an amplitude-modulated video signal are automatically adjusted. For adjustment of the depth of modulation, a sync tip of the video signal is sampled, corrected and normalized to a reference level, e.g., a 50% video level. A reference pulse is inserted into the video signal, e.g., in a sync pulse or in lines  22  and/or  23  of the vertical blanking interval. The reference pulse is sampled and compared to the normalized sync tip pulse to determine an error. The error is converted to an adjustment signal for a charge pump which increases or decreases the depth of modulation accordingly. For adjustment of the absolute carrier level, the insertion of a reference pulse is not required. Instead, a reference value is stored in a memory and retrieved for comparison with the corrected sync tip pulse. An error term is computed and converted to an adjustment signal for a charge pump which increases or decreases the absolute carrier level accordingly. Several modulation circuits can share a common microprocessor controller.

BACKGROUND OF THE INVENTION

The present invention relates to an apparatus for automaticallycontrolling the amplitude modulation of video signals. Both the absolutecarrier level and the depth of modulation are controlled. The inventionis suitable for use with unscrambled television signals as well astelevision signals that have the horizontal synchronization pulsesuppressed to prevent detection of the signals by unauthorized persons,e.g., pirates.

A composite video signal such as one which conforms to the NTSC standardincludes picture luminance and chrominance information as well as timinginformation for the synchronization of scanning and color processingcircuits at a receiver. At the end of each line scan at the receiver, ahorizontal synchronizing pulse (HSYNC) commands the scanning circuit toreturn the scanning beam to the left of the screen to begin scanning anew line. Similarly, at the completion of each field or frame, avertical synchronizing pulse (VSYNC) commands the scanning circuit toreturn to the top of the screen to begin scanning the next field orframe. The return period is known as the vertical blanking interval.

Accordingly, the television signal may be scrambled by altering thenormal position and/or amplitude of the synchronization pulses. Suchtechniques for scrambling the video portions of television signals arewell known. For example, U.S. Pat. No. 3,813,482 to Blonder discloses asystem for transmitting television signals where the video is scrambledby suppressing the vertical or horizontal synchronization pulses toproduce a shifting or rolling scrambled picture. U.S. Pat. No. 4,542,407to Cooper et al. discloses an apparatus for scrambling and descramblingtelevision programs in which the horizontal synchronization informationis suppressed at a cable television (CATV) headend, and then regeneratedby a subscriber's cable television converter. U.S. Pat. Nos. 4,095,258to Sperber, 4,163,252 to Mistry et al., and 4,571,615 to Robbins et al.describe schemes for decoding scrambled television signals.

In particular, by suppressing the horizontal synchronization pulsesbelow the average value of the active video, a television receiverattempts unsuccessfully to lock horizontally on to random peaks of theactive video rather than the HSYNC pulses. Additionally, the loss ofeffective horizontal synchronization prevents the receiver from properlyutilizing the color burst signal which is associated with the HSYNCpulse, so that color reproduction is also faulty.

In order for a receiver to restore (i.e., descramble) the scrambledvideo signal, the suppressed synchronization pulses must be restored.This may be accomplished by amplitude modulating timing pulses on the FMaudio carrier of the television signal. The pulses are then detected inthe audio portion of the receiver and used to generate the timingsignals necessary to descramble the received video signal.Alternatively, a portion of the sync timing pulses is transmittedwithout suppression, for example, during the vertical blanking interval.The receiver is phase-locked to the unsuppressed signals to create therequired timing and synchronization information for descrambling thevideo portion of the signal.

Further scrambling of a television signal may be achieved by inverting aportion of the active video such as described in U.S. Pat. No. 4,598,318to Robbins.

Generally, amplitude modulation of the active video is achieved byvarying the amplitude of an RF carrier signal about a fixed level. Thevariation in amplitude is known as the depth of modulation.Additionally, synchronization signals can be suppressed to −6 dB or −10dB below the unsuppressed level which is specified by the transmissionstandard which is used, e.g., −40 IRE for NTSC signals. The suppressionlevel may be varied with time, for example, according to detected scenechanges in the active video. Switching may occur several times persecond, or more slowly, such as once every several seconds.Conventionally, a stable amplitude modulator is used with automatic gaincontrol of the video signal.

However, suppression and subsequent restoration of synchronizationpulses is hampered by variations in amplitude modulation equipment,which may be at a CATV headed or a remote location, for example.Conventional RF carrier circuitry is subject to drift and otherinaccuracies due to humidity and temperature variations, as well aschanges due to degradation over the lifetime of the equipment, forexample. Modulation level discrepancies can cause flickering or otherundesirable brightness changes in the recovered video image.

Thus, such modulating circuitry must be periodically adjusted by atechnician using metering equipment to ensure accuracy. This solution isinefficient, in particular, when the modulation circuitry is remotelylocated. Additionally, the problem of drift in the modulation accuracyis not solved.

Accordingly, it would be desirable to have a system for automaticallycontrolling the amplitude modulation level and depth of modulation of atelevision signal. The system should be suitable for use with syncsuppressed signals, including signals with VSYNC and/or HSYNCsuppression, as well as non-suppressed signals. The system should besuitable for use with multiple levels of sync suppression. The systemshould also be suitable for use with signals with normal (e.g.,non-inverted) as well as inverted active video portions.

The system should further be relatively inexpensive to manufacture andinstall, and should require only a low-speed microprocessor controller.The system should provide an assembly with a common microprocessorcontroller which services a number of individual modulation circuits ona time-sharing basis.

The present invention provides a system having the above and otheradvantages.

SUMMARY OF THE INVENTION

In accordance with the present invention, an apparatus is presented forautomatically controlling the amplitude modulation of a video signal.

In one embodiment, an automated modulation circuit for processing avideo signal comprises means for detecting a comparison portion in thevideo signal having an associated amplitude. The comparison portion maybe a horizontal or vertical synchronization pulse. For example, ahorizontal sync pulse may have a sync pulse tip at −40 IRE (at baseband)for a non-scrambled video signal. Means are provided for normalizing thecomparison portion amplitude according to a reference level. Thereference level may correspond to a video level, e.g., 50 IRE, aboutwhich inversion of the active video occurs. However, inversion is notrequired. Normalization involves scaling the comparison portion to thereference level using a multiplier.

Means are provided for detecting a reference pulse having a referencepulse amplitude at the reference level in the video signal. For example,a reference pulse may be provided in a horizontal or vertical syncpulse, or in a vertical blanking interval. The reference pulse may serveas an inversion level pulse when inversion occurs.

Means are provided for generating a first error signal corresponding toa difference between the normalized sync pulse tip amplitude and thereference pulse amplitude. For example, sample and hold circuits mayobtain samples of the sync pulse tip and the reference pulse. An A/Dconverter converts the samples to digital form for processing by amicroprocessor controller, which then determines an appropriate errorsignal based on the relative magnitudes of the two samples.

Means responsive to the first error signal adjusts a depth of modulationof the video signal. The first error signal can bias the video signalprior to modulation by an RF carrier.

When the sync pulse tip is attenuated, e.g., in a scrambled signal,means are provided for correcting the comparison portion amplitude toremove the attenuation. For example, a comparison portion which is async pulse tip may be attenuated by 6 dB or 10 dB, in which caseappropriate multipliers are used to restore the sync pulse tip to the−40 IRE level, or to another non-attenuated level depending on the videostandard in effect.

The means for generating a first error signal generates an error signalcorresponding to a difference between the normalized and correctedcomparison portion amplitude and the reference pulse amplitude.

The means responsive to the first error signal for adjusting a depth ofmodulation of the video signal comprises a microprocessor controller forconverting the first error signal to a first adjustment signal. This maybe achieved, for example, using a memory which stores a look up tablefor converting the error signal to an adjustment signal. Thresholdranges may be used to provide a range where a zero or near zero errorsignal results in a zero adjustment signal. The adjustment signal mayfurther be a function of a bit error of the error signal. A first chargepump receives the adjustment signal and provides a correspondingmodulation depth control signal, which is coupled to bias the videosignal prior to modulation of the video signal by an RF carrier.

Moreover, while the comparison portion may be compared to a 50% videolevel, for example, other comparison portions and reference portions ofthe video signal may be used. For example, it is possible to compare ablanking level to the 50% video level or to another video level, or tocompare the sync tip level to the blanking level.

An RF carrier reference level corresponding to an RF carrier of thevideo signal may be provided. This may be a value which is stored inmemory and retrieved for later use by the microprocessor. Means areprovided for generating a second error signal corresponding to adifference between the sync pulse tip amplitude prior to normalizing andthe RF carrier reference level. Means responsive to the second errorsignal adjusts an amplitude of the RF carrier. For example, the seconderror signal may be coupled to a voltage controlled attenuator (VCA) foradjusting the output of an RF carrier generator. The video signal atbaseband is then modulated on to the adjusted RF carrier.

The means responsive to the second error signal for adjusting anamplitude of the RF carrier comprises a microprocessor controller forconverting the second error signal to a second adjustment signal. Forexample, the same microprocessor controller may be used for processingthe first and second error signals on a time sharing basis. A secondcharge pump receives the second adjustment signal and provides acorresponding RF amplitude control signal.

Thus, automated control can be provided for both the depth of modulationand the absolute RF carrier level to correct for drift and otherinaccuracies which may occur over time, or to provide a more constantchannel power, if that is a goal.

An automated modulation assembly for processing a plurality of videosignals comprises a plurality of the above-described circuits.Manufacturing several, e.g., four, of the modulation circuits on acommon assembly can provide an economical apparatus since a singlemicroprocessor control and associated memory can be shared by theindividual modulation circuits on a time-sharing basis. Each individualmodulation circuit is used for modulating a corresponding video signal,e.g., channel or programming service.

The microprocessor controller converts the first error signal of each ofthe individual circuits to corresponding first adjustment signals. Eachcircuit includes its own first charge pump for receiving thecorresponding first adjustment signal and providing a correspondingmodulation depth control signal.

In a second embodiment, an automated modulation circuit for processing avideo signal comprises means for detecting a comparison portion with anassociated amplitude, means for providing an RF carrier reference levelcorresponding to an RF carrier of the video signal, means for generatingan error signal corresponding to a difference between the comparisonportion amplitude and the RF carrier reference level, and meansresponsive to the error signal for adjusting an amplitude of the RFcarrier.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 illustrates an amplitude versus time sketch of a conventionaltelevision signal.

FIG. 2 illustrates an amplitude versus time sketch of a televisionsignal with an inverted video portion and an inversion level (reference)pulse.

FIG. 3 illustrates a modulated carrier in accordance with the presentinvention.

FIG. 4 illustrates a number of cycles of a modulated carrier inaccordance with the present invention.

FIG. 5 illustrates an automatic modulation depth control process inaccordance with the present invention.

FIG. 6 illustrates an automatic RF carrier level control process inaccordance with the present invention.

FIG. 7 is an illustration of an automatic modulation control circuit inaccordance with the present invention.

FIG. 8 is a block diagram of a scheme for providing automatic amplitudemodulation of several video channels using a common microprocessorcontroller.

DETAILED DESCRIPTION OF THE INVENTION

An apparatus is presented for automatically controlling the amplitudemodulation of video signals.

FIG. 1 illustrates an amplitude versus time sketch of a conventionaltelevision signal. The trace shown is a baseband signal since it has notyet been modulated with an RF carrier. The amplitude of the voltage ofthe signal is expressed in IRE units as established by the Institute ofRadio Engineers in the example shown. A blanking level (i.e., frontporch) 100, corresponding to zero IRE units precedes a sync pulse 110,which is at a synchronization level of −40 IRE. The sync pulse shown isa horizontal sync pulse, although the invention can be usedalternatively, or in addition, with a vertical sync pulse, or otherpredetermined level. Moreover, the sync level shown denotes anunscrambled signal. With a scrambled signal, the sync pulse isattenuated from the level shown by −6 dB or −10 dB, for example. Theinvention may be used with scrambled or unscrambled signals.

Another blanking level signal (i.e., back porch) 115 follows the syncpulse 110. Next, a color burst 120, which is 8-10 cycles at 3.58 MHz, isprovided. Subsequently, an active video region 130 is provided. Theactive video region is shown having a smooth curved shape forsimplicity. Another blanking level 140 follows the active video 130.

Suppression of the sync pulse 110 can be achieved by passing theamplitude-modulated television signal through a 6 dB or 10 dB attenuatorduring a sync suppression time which extends for a period of about 12μsec., namely from 18 μsec. before the sync pulse 110 to about 5.7 μsec.after the sync pulse 110.

The power level of a transmitted scrambled signal can be increased,e.g., by 3 dB when the sync tip is suppressed to improve the overallsignal-to-noise ratio.

FIG. 2 illustrates an amplitude versus time sketch of a televisionsignal with an inverted video portion. With this scrambling technique,as disclosed in U.S. Pat. No. 4,598,318 to Robbins, an inversion levelpulse 150 is provided in the sync pulse 110 to designate an amplitudelevel about which the active video is inverted. In the example shown,the inversion level pulse has an amplitude of 50 IRE, so the activevideo is inverted about an amplitude, shown by a line 170, at 50 IRE.The inverted video 160 is essentially a mirror image of the non-invertedactive video 130 of FIG. 1. All or only randomly selected lines of avideo field or frame may be inverted. 50 IRE is a convenient level touse since it is half way between the white level at 100 IRE and theblanking level at 0 IRE. 50 IRE may be considered to be a 50% videolevel since the video extends from 0-100 IRE. This should not beconfused with percent depth of modulation discussed below.

Other inversion levels may be used, such as 30 IRE, which is themidpoint of the range from −40 to 100 IRE. The reference pulse may beprovided in addition to the inversion level pulse when the two differ,but it is convenient to use the inversion pulse as a reference pulse ifpossible. Any signal which has active video below the blanking level isassumed to be inverted, since somewhere in every field there would besome gray (white) video normally.

In accordance with the present invention, the pulse 150 can serve as areference level for adjusting the modulation of the television signal.Even if the active video is not inverted, and/or the sync pulse is notattenuated, the reference pulse 150 can be inserted into the sync pulse110 or other predetermined location in the video signal. For example,lines 22 and/or 23 of the vertical blanking interval may be used. Use ofthese lines makes it difficult to observe when inversion on line 24takes place. Any modulator can be modified to provide the referencepulse.

FIG. 3 illustrates a modulated carrier in accordance with the presentinvention. The modulated carrier corresponds to the baseband signal ofFIG. 2. The corresponding IRE level of the modulated carrier is shown onthe vertical axis. The modulated carrier is obtained by modulating thebaseband signal of FIG. 2 with an RF sine wave carrier, for example, at45.75 MHz. The baseband signal is in the range from 0-4.2 MHz with theNTSC standard. The waveform is essentially symmetric about a centralhorizontal axis at the corresponding IRE level of zero. Regions 300,310, 350, 315, 320, 360 and 340 correspond, respectively, to regions200, 210, 250, 215, 220, 260 and 240 in FIG. 2.

The sync tip 310 is assumed to be at a corresponding IRE level of 160,whether it is suppressed or not, while the inversion pulse 350, whichrepresents a 50% video level (50 IRE at baseband), is at an IRE level of70. Thus, to normalize the sync tip to the 50% video level, the sync tipshould be multiplied by a factor of {fraction (70/160)}×=0.4375. Inother words, in the modulated signal, the signal voltage of the 50%reference level is 43.75% of the signal voltage of the sync tip. Thiscorresponds to a depth of modulation of {fraction (90/160)}=0.5625 or56.25% since the 70 IRE level is 90 IRE below the 160 IRE level. The 0IRE level corresponds to a depth of modulation of {fraction(160/160)}=100%. Generally, the region between 87.5% and 100% modulationdepth is maintained to permit intercarrier detection of the audiosignal, so the 20 IRE level at 87.5% depth of modulation is the maximumrealized.

Likewise, to normalize the blanking level at 120 IRE to the 50%reference level at 70 IRE, the blanking level should be multiplied by afactor of {fraction (70/120)}=0.583. To normalize the sync tip at 160IRE to the blanking level at 120 IRE, the sync tip should be multipliedby a factor of {fraction (120/160)}=0.75. Generally, any comparisonportion can be compared to any reference portion of the video signal byusing an appropriate multiplier. Other examples can be realized in viewof the above

As will be seen, it is possible to normalize a comparison portion of themodulated video signal to a reference level to determine whether thedepth of modulation is correct.

FIG. 4 illustrates a number of cycles of a modulated carrier inaccordance with the present invention. The signal shows a non-invertedactive video portion with a valley 410 which corresponds to the peak ofthe active video 130 of FIG. 1. Sync tip peaks 400 correspond to thepeak 310 of FIG. 3. Regions 405 and 415 correspond to regions 315 and300, respectively, of FIG. 3. The depth of modulation is shown extendingfrom 0% at the sync tip peak to 100% at the zero signal level. Thenegative amplitudes of the signal are a mirror image of the positiveamplitudes.

FIG. 5 illustrates an automatic modulation depth control process inaccordance with the present invention. The process starts at block 500.At block 502, the sync tip of the television signal is sampled. Thisvalue, designated A_(S), may correspond to −40 IRE (at baseband), −6 dBor −10 dB of a non-attenuated level, or some other attenuated level. Atblock 504, the sampled sync value is corrected for attenuation, ifrequired. For example, at block 506, if the attenuation is −6 dB, A_(S)is multiplied by 2.0 to obtain the corrected value A_(SC)(since−20*log₁₀(2.0)=−6). At block 508, if the attenuation is −10 dB,A_(S) is multiplied by 3.162 to obtain the corrected value A_(SC)(since−20*log₁₀(3.162)=−10) If the television signal is not scrambled,e.g., in the clear, the sync tip will not be suppressed, so processingwill continue directly at block 510, thereby bypassing blocks 506 and508. Regarding blocks 506 and 508, other multipliers should be used ifother attenuation levels are used.

At block 510, the corrected sync tip sample, A_(SC), is normalized to areference level. For example, to normalize A_(SC) to a value of 50 IRE(at baseband), as discussed previously, A_(SC) is multiplied by 0.4375at block 512. Sampling may be realized using an eight bit A/D converterwhich is built into a microprocessor. Multiplication by 0.4375({fraction (7/16)}) can be achieved using integer arithmetic byperforming four right shifts to obtain {fraction (1/16)} of the originalvalue, right shifting the original value once to obtain ½ of theoriginal value, then subtracting the {fraction (1/16)} value from the ½value to obtain {fraction (7/16)} of the original value.

For example, assume an arbitrary A_(SCN) of 221 in decimal, denoted221₁₀, or in binary, 11011101₂. Right shifting once yields 01101110(e.g., 110₁₀ or {fraction (221/2)}). Right shifting twice yields00110111 (e.g., 55₁₀ or {fraction (221/4)}). Right shifting three timesyields 00011011 (e.g., 27₁₀ or {fraction (221/8)}). Right shifting fourtimes yields 00001101 (e.g., 13₁₀ or {fraction (221/16)}). Subtractioncan be performed using 2's complement notation. Specifically, the{fraction (221/2)}value (01101110) is added to the 2's complement of the{fraction (221/16)}value, namely 11110011, to obtain01100001=97₁₀=221*({fraction (7/16)}).

Virtually any reference level may be selected. For example, it ispossible to compare a blanking level which is normalized using anappropriate multiplier to the 50% video level or to another video level.Specifically, for a 50% video reference level, a multiplier of 0.583 isused as discussed in connection with FIG. 3.

Alternatively, the sync tip level may be normalized and corrected usingan appropriate multiplier for comparison with the blanking level. Forexample, a multiplier of 0.75 is used as discussed in connection withFIG. 3. Correction of the attenuation of the sync tip level is performedif required.

Generally, any predetermined portion of the video signal may be comparedto any selected reference level, with appropriate correction andnormalization. The portion of the signal which is compared to thereference level may be referred to as a “comparison portion” of thevideo signal, while the reference level is obtained from a “referenceportion” of the video signal. For example, it may be desirable to use acomparison portion other than the sync tip since the use of the sync tipis sometimes a problem when it is compressed by the modulation process.

The example of FIG. 5, where the sync tip is compared to the 50% videolevel is convenient since 50 IRE is often taken as an inversion levelfor television signals which use inversion of the active video toenhance scrambling. Generally, the sync tip sample is normalizedaccording to the level of the reference pulse which will be sampled forcomparison with the normalized sync tip sample. At block 514, thenormalized and corrected sync tip value A_(SCN) is stored for laterused, e.g., at block 524, discussed below, and/or block 612, discussedin connection with FIG. 6.

At block 516, the reference pulse is sampled to obtain a reference valueA_(R). As mentioned in regard to FIG. 3, the reference pulse may be aninversion level pulse in a sync pulse which is used for inverting theactive video. The reference pulse is inserted in the video signal evenif no inversion or other scrambling is performed. For example, thereference pulse may be inserted in line 22 of the vertical blankinginterval. At blocks 518, 520 and 522, A_(R) is corrected forattenuation, if required, in the same manner as discussed above inconnection with blocks 504, 506 and 508, respectively, to obtain thecorrected reference value A_(RC).

At block 524, a modulation depth delta term Δ_(MD) is calculated asΔ_(MD)=A_(SCN)−A_(RC). Essentially, A_(SCN) is what the signal levelshould be at the reference level of modulation depth, and A_(RC) is whatthe signal level is. Thus, at block 526, if Δ_(MD) is too low, e.g.,less than zero, or less than a threshold value below zero, themodulation depth should be increased. This can be accomplished byincreasing a charge pump value as discussed in connection with FIG. 7.At block 528, if Δ_(MD) is too high, e.g., greater than zero, or greaterthan a threshold value above zero, the modulation depth should bedecreased. This can be accomplished by decreasing a charge pump value.The threshold value may correspond to a one-bit error when integerarithmetic is used. Generally, the resolution of the error depends onthe demodulator linearity and A/D resolution. The adjustment (i.e.,correction) resolution is usually set to make each adjustment stepsmaller than the measured error. Even with that condition, single biterrors can be ignored, and two-bit errors can be treated as if they wereone bit errors. Alternatively, a threshold value of zero may be used.The threshold value essentially defines a band or range about zero whereno modulation adjustment occurs.

The process ends at block 530, but is periodically repeated for eachchannel. It may be desirable to process a subsequent sample from thesame channel, or to process samples from other channels on a rotatingbasis. The rate of drift of the modulation circuitry is expected to berelatively small, so the period for repeating the process can berelatively long, e.g., several seconds or minutes-or even longer. Sincethe repetition frequency is small, low speed, inexpensive circuitry canbe used. Additionally, a single microprocessor can be used for themodulation circuitry of several different channels.

FIG. 6 illustrates an automatic RF carrier level control process inaccordance with the present invention. The process may be combined withthe process of FIG. 5, or used in a separate control loop. The processbegins at block 600. At block 602, a comparison portion such as a synctip sample value A_(S) is obtained. This may be the same as block 502 inFIG. 5, in which case the sample may be obtained from memory if storedpreviously. Blocks 604, 606 and 608 correspond to blocks 504, 506 and508, respectively, of FIG. 5.

At block 610, an RF amplitude reference value A_(RF) is retrieved. Thisreference portion may be the expected value of 100% of the RF sine wavewhich is combined with the baseband television signal to obtain amodulated television signal. This reference value, which depends on theparticular modulation equipment used, can be retrieved from a memoryunder the control of a microprocessor.

At block 612, an RF amplitude delta term Δ_(RF) is calculated asΔ_(RF)=A_(SC)−A_(RF). Essentially, Δ_(RF) is what the signal levelshould be, and A_(SC) is what the signal level is. Thus, at block 614,if Δ_(RF) is too high, e.g., greater than zero, or greater than athreshold value above zero, the RF carrier amplitude should bedecreased. This can be accomplished by decreasing a charge pump value asdiscussed in connection with FIG. 7. At block 616, if Δ_(RF) is too low,e.g., less than zero, or less than a threshold value below zero, the RFcarrier amplitude should be increased. This can be accomplished byincreasing a charge pump value. The threshold value may correspond to aone bit error when integer arithmetic is used. Alternatively, athreshold value of zero may be used.

The process ends at block 618, but is periodically repeated for eachchannel (e.g., programming service). It may be desirable to process asubsequent sample from the same channel, or to process samples fromother channels on a rotating, e.g., time sharing, basis.

The RF carrier level control process may generally use any comparisonportion and any reference portion. For example, the comparison portionmay be a sync pulse tip or a blanking level, and the reference portionmay be a blanking portion or 50% video level.

FIG. 7 is an illustration of an automatic modulation control circuit inaccordance with the present invention. The circuit, shown generally at700, may be located at the headend of a CATV systems or at a remotelocation, for example. A scrambled video signal generator 705 receives aclear (i.e., unscrambled) video input signal and optionally scramblesthe signal, for example, by suppressing the horizontal and/or verticalsync pulses, and/or by inverting the active video. The scrambled videosignal generator 705 sends a control signal via a path 706 to amicroprocessor controller 710 which indicates whether the signal isscrambled, and, if so, at what level, e.g., −6 dB or −10 dB, forexample. “Clear” indicates a non-scrambled signal. Additionalinformation as to which reference levels are being used and what modesof operation are in use can also be transmitted to the microprocessorcontroller on the path 706.

The scrambled video signal generator 705 further provides a sync tipsample-and-hold (S/H) control signal to a switch 715, while a reference(ref.) S/H control signal is provided to a switch 720. The sync tip S/Hcontrol signal commands the switch 715 to close during a synchronizationperiod when the sync tip is being output by the signal generator 705.When the switch 715 closes, the sync tip sample A_(S) discussed inconnection with FIG. 5 is provided to a sync tip S/H circuit 725.Otherwise the switch 715 is open.

Similarly, the reference S/H control signal commands the switch 720 toclose when it is desired to provide a reference signal sample A_(RF) toa reference S/H circuit 730. Each of the S/H circuits 725 and 730include conventional components such as capacitors and amplifiers whichmaintain the voltage of the input signal in a known manner. Themicroprocessor controller 710 sends a control signal to a switch 735 tocouple the signal voltage from the desired S/H circuit 725 or 730 to ananalog-to-digital (A/D) converter 740. The A/D converter 740 alsoreceives control signals from the microprocessor controller 710. Aneight-bit A/D converter may be used. Additionally, the A/D converter 740may be built into the microprocessor controller 710.

The A/D converter 740 and the microprocessor controller 710 perform thevarious steps indicated in FIGS. 5 and 6. For example, regarding theprocess of FIG. 5, the sync tip value A_(S) is corrected forattenuation, if required, normalized to a reference level, and stored,while the sample reference pulse is also corrected for attenuation, ifrequired. The delta modulation depth term Δ_(MD) is also calculated.

Regarding the process of FIG. 6, the microprocessor controller 710obtains the values A_(SC) A_(RF) and Δ_(RF).

The video signal which is output from the scrambled video signalgenerator 705 is coupled to a modulator 760 via a capacitor C₁, andbiased by a resistor R₁ which prevents shorting out of the video signal.A capacitor C₂ is optionally used to stop hum and noise from gettinginto the video signal, but is not required. The modulator 760 modulatesthe video signal using an RF carrier from an RF carrier generator 780which is processed by a voltage controlled attenuator (VCA) 770. The VCAis responsive to an RF amplitude control signal to adjust the absolutelevel of the RF carrier.

The video signal output from the generator 705 is similarly biased by amodulation depth control signal which is received by the resistor R₁.The RF amplitude control signal is provided by a charge pump 750 inresponse to an adjustment signal from the microprocessor controller 710.The microprocessor controller 710 may communicate with a memory (e.g.,RAM) 712 which may store a look up table for converting Δ_(MD) andΔ_(RF) to corresponding adjustment signals for charge pumps 750 and 755.The memory 712 may also store values such as A_(SC) for use in both theprocesses of FIGS. 5 and 6 to avoid the need to obtain two samples. Thememory 712 may optionally be internal to the microprocessor controller710.

The charge pumps 750 and 755 each contain a diode pair, the output ofwhich is capacitively coupled to ground and provided to an amplifier.Each charge pump communicates with the microprocessor controller 710 viatwo lines which bias the diode pair. Specifically, the delta inmodulation depth Δ_(MD) will be translated to an adjustment signal forthe charge pump 755 to provide an increased charge to increase the depthof modulation when the corrected and normalized sync tip sample levelA_(SCN) is less than the corrected reference level A_(RC), or to providea decreased charge to decrease the depth of modulation whenA_(SCN)>A_(RC).

Additionally, the delta in RF carrier amplitude Δ_(RF) will betranslated to an adjustment signal for the charge pump 750 to provide anincreased charge to increase the RF carrier amplitude when the correctedsync tip sample level A_(SC) is less than the reference level A_(RF), orto provide a decreased charge to decrease the RF carrier amplitude whenA_(SC)>A_(RF).

Resistors R₃-R₆ in series with the diodes of the charge pumps 750 and755 limit the amount of charge which can be transferred to or from thecapacitor in the charge pump (e.g., capacitor C₄ in charge pump 750 andcapacitor C₅ in charge pump 755). The charge is also limited by theamount of time over which the charging or discharging of the capacitoroccurs. Typically a single short pulse either charges or drains enoughcharge to change the voltage on the capacitor less than one LeastSignificant Bit (LSB) of the A/D converter 740.

The video signal which is output from the modulator 760 is provided to achannel up converter, for example, for transmission over a CATV network,and to a video detector 790. The video detector 790 includes a diodewhich is capacitively coupled to ground via a capacitor C₃. A resistorR₂ is coupled in parallel. The diode is a rectifier, so if the waveformcoming from the modulator 760 is a carrier with video modulationimposed, only the positive going half of the carrier waves will passthrough the diode. The capacitor C₃ stores the value of the peak of thecarrier, while the resistor R₂ leaks the signal off of the capacitor sothat the capacitor is not charged up to the peak value, at which pointit stops detecting.

The capacitor/resistor value are chosen to be able to discharge at arate to follow the highest modulating frequency while, at the same time,the carrier frequency is high enough to allow the capacitor to followthe carrier waveform envelope. Since the ratio of the carrier tomodulation is about ten, there are ten carrier waves for each of thehighest modulating frequency, which is 4.2 MHz with the NTSC standard.

The modulation circuit 700 can operate in two control loops, one for thedepth of modulation and one for the absolute carrier level. Thus, theupdate period can be different for each loop. Additionally, the circuit700 can operate in only one of the modes, if desired. The optimal updaterate depends on a variety of factors, including the humidity of thelocation of the charge pumps and the quality of the capacitors anddiodes. Transistor base-collector junctions may be used as the diodesbecause of their superior low leakage qualities.

FIG. 8 is a block diagram of a scheme for providing automatic amplitudemodulation of several channels using a common microprocessor controller.Further efficiencies can be achieved by fabricating several circuitswith a common microprocessor controller. Dedicated microprocessorcontrollers for each channel are not required since the errors are smalland slowly changing. Thus, the processing cycle can be very slow, e.g.,several seconds or minutes or longer.

A circuit for providing automatic amplitude modulation of three videochannels while using a common microprocessor controller and memory isshown in simplified form at 800. The number of channels which can beserviced by one microprocessor controller will depend on the speed ofthe microprocessor and the desired update cycle.

Signals from video channels A, B and C are input to respective signalgenerators 805, 810 and 815. Processing of the respective channels isshown at processing blocks 820, 830 and 840. The processing includesmodulation, sample-and-hold circuits, and charge pumps for each channelas discussed in connection with FIG. 7. A microprocessor controller 850which communicates with a memory 860 controls or services each of thechannels on a time-sharing basis. For example, first channel A isserviced to adjust the modulation as required, then channel B, and thenchannel C. The cycle repeats again with channel A.

Accordingly, it can be seen that the present invention provides anapparatus for automatically adjusting the depth of modulation and theabsolute carrier level of a video signal.

For adjustment of the depth of modulation, a sync tip of the videosignal is sampled, corrected and normalized to a reference level, e.g.,a 50% video level. A reference pulse is inserted into the video signal,e.g., in a sync pulse or in lines 22 and/or 23 of the vertical blankinginterval. The reference pulse is sampled and compared to the normalizedsync tip pulse to determine an error. The error is converted to anadjustment signal for a charge pump which increases or decreases thedepth of modulation accordingly.

The use of a sync tip as a comparison portion and the 50% referencelevel as a reference portion are only example embodiments, as othercombinations can be used. For example, the blanking level may becompared to the 50% level, or the sync tip level may be compared to theblanking level.

For adjustment of the absolute RF carrier level, the insertion of areference pulse is not required. Instead, a reference value is stored ina memory and retrieved for comparison with the corrected sync tip pulse.An error term is computed and converted to an adjustment signal for acharge pump which increases or decreases the absolute carrier levelaccordingly.

Advantageously, the scheme provides automatic modulation control therebyobviating the need for periodic manual adjustments. The requiredcircuitry can be manufactured at a relatively low cost and is suitablefor use in remote locations. The present invention is believed to beparticular suitable for use in developing CATV markets where low-cost,low-maintenance equipment is required.

Further efficiencies can be achieved by fabricating several circuitswith a common microprocessor controller and memory which service theindividual circuits on a time-sharing basis.

Although the invention has been described in connection with variousspecific embodiments, those skilled in the art will appreciate thatnumerous adaptations and modifications may be made thereto withoutdeparting from the spirit and scope of the invention as set forth in theclaims.

For example, while the invention was discussed in connection with anNTSC video signal, video signals corresponding to other standards, suchas PAL, may also be used.

What is claimed is:
 1. An automated modulation circuit for processing avideo signal, comprising: means for detecting a comparison portion ofsaid video signal; said comparison portion having an associatedamplitude; means for normalizing the comparison portion amplitudeaccording to a reference level which is different from the associatedamplitude; means for detecting a reference portion of said video signalhaving an amplitude at the reference level in said video signal; meansfor generating a first error signal corresponding to a differencebetween the normalized comparison portion amplitude and the referenceportion amplitude; and adjustment means responsive to said first errorsignal for adjusting a depth of modulation of said video signal, saidadjustment means comprising: a microprocessor controller for convertingsaid first error signal to a first adjustment signal; and a first chargepump for receiving said adjustment signal and providing a correspondingmodulation depth control signal; wherein said corresponding modulationdepth control signal is coupled to bias the video signal prior tomodulation of said video signal by an RF carrier.
 2. The circuit ofclaim 1, wherein: said reference portion is a reference pulse which ispositioned within a sync pulse of said video signal.
 3. The circuit ofclaim 1, wherein: said reference portion is a reference pulse which ispositioned within a vertical blanking interval of said video signal. 4.The circuit of claim 1, wherein said comparison portion is an attenuatedsync pulse tip, further comprising: means for determining the degree ofattenuation of the sync pulse tip and providing a corresponding controlsignal to said microprocessor controller; wherein: said microprocessorcontroller corrects the sync pulse tip amplitude to remove theattenuation according to said control signal; and said means forgenerating a first error signal generates an error signal correspondingto a difference between the normalized and corrected sync pulse tipamplitude and the reference amplitude.
 5. The circuit of claim 1,wherein said comparison portion is an attenuated sync pulse tip, furthercomprising: means for correcting the sync pulse tip amplitude to removethe attenuation; wherein said means for generating a first error signalgenerates an error signal corresponding to a difference between thenormalized and corrected sync pulse tip amplitude and the referenceamplitude.
 6. An automated modulation circuit for processing a videosignal, comprising: means for detecting a comparison portion of saidvideo signal; said comparison portion having an associated amplitude;means for normalizing the comparison portion amplitude according to areference level which is different from the associated amplitude; meansfor detecting a reference portion of said video signal having anamplitude at the reference level in said video signal; means forgenerating a first error signal corresponding to a difference betweenthe normalized comparison portion amplitude and the reference portionamplitude; means responsive to said first error signal for adjusting adepth of modulation of said video signal; means for providing an RFcarrier reference level corresponding to an RF carrier of said videosignal; means for generating a second error signal corresponding to adifference between the comparison portion amplitude prior to normalizingand the RF carrier reference level; and means responsive to said seconderror signal for adjusting an amplitude of said RF carrier.
 7. Thecircuit of claim 6, wherein said means responsive to said second errorsignal for adjusting an amplitude of said RF carrier comprises: amicroprocessor controller for converting said second error signal to asecond adjustment signal; and a second charge pump for receiving saidsecond adjustment signal and providing a corresponding RF amplitudecontrol signal.
 8. The circuit of claim 7, wherein: said microprocessorcontroller is adapted for use in converting said first error signal to afirst adjustment signal, and providing said first adjustment signal to afirst charge pump to enable said first charge pump to provide acorresponding modulation depth control signal.
 9. The circuit of claim6, wherein: said comparison portion is a sync pulse tip.
 10. The circuitof claim 1, wherein: said reference portion is used as an inversionlevel pulse for the video signal.
 11. The circuit of claim 1, wherein:said comparison portion is a blanking portion of the video signal. 12.The circuit of claim 1, wherein: said reference portion is a 50% videolevel.
 13. The circuit of claim 1, wherein: said comparison portion is async pulse tip.
 14. The circuit of claim 13, wherein: said referenceportion is a blanking portion of the video signal.
 15. An automatedmodulation assembly for processing a plurality of video signals,comprising a plurality of the circuits of claim 1, wherein: themicroprocessor controller operates on a time-sharing basis to convertthe first error signal of each of said circuits to corresponding firstadjustment signals; and the first charge pump of each of said circuitsreceives the corresponding first adjustment signal and provides acorresponding modulation depth control signal.